Frequency modulation receiver



Ju1y4, 195o w. R. KOCH 2,513,727

FREQUENCY MODULATION RECEIVER Filed Aug. 3, 1945 IN VEN TOR. WNF/fw /8 foc/vl Patented July 4, 1950 FREQUENCY MODULATION Wineld R. Koen, gaddonield, N. J., assigner to Radio `Corporation of America, a corporation of Delaware" ApplicationAv August 3, 1945, Serial No. 608,677 3 (Cl. 25o-20) My `presi-irrt invention generally rele-.ter to improvement in receivers of ariel@ .modul t d Carrier Waves, .aud more oartioiil rlv to .proved frequency modulation re In the reception of angle Waves it is necessary that `the ,f the ooiriodulator of the receiver .te presente@ vvitlfi modulated carrier waye energy Whose Varri; pltuolo variations areas aoolirete reerellla.- tion of the angle modulations of the received Waves. This is insured by omolorioe aiiaiiirll: Itude limiting device prior to l'the discringinator @Chmn 0f the .dlmplltpl S0 as. 150 :Wel/@Tit 1111.7 desired aniplitude variations .in trie rec commonly used ,in accordance ,vvitlithe Seeley patent, the vdis c`r`iir1iiviator section comprises/'a pair of coupled resonant circuits each tuned Ato a predetermined operating frequency Trielat lter is usually .tneintermediate I.itrequericy r, QI. 152) of Aa receiver of .the ViWidely-veeolfSlilotfliotoroolruo type The primary-.ofthe two oo ,i usually included in Atheplate' circuit i luniter tube. A pair kof opposed rectier vdevices are connected to yopposed A ends of trie secondary circuit coil, which is center-tapped. Thefrecti cd voltages developed across the respective outn put load resistors of the rectifier .devices yare combined in polarity opposition, and'tljieresnltf ant voltage is accurately representative of .tide frequency variations of the Ireceived FM vvaves.

The Well ,known frequency deviation vs. volt- Y age output characteristic .of the Seeley Kdembdu lator system is generally an inclinedapprogimately linear characteristic Whose upper ,and lower ends are bent in opposite directions. The

linearityof the characteristic depends upon the degree voffciiiplir 1gA .between .the primary andsecf ondary circuits of the discriminator section, L.and tire` erective selectivityoi these circuits. Usually the coupling is vapproxirnately critical coupling, einer .vliiolli sersiitioeilio ,Primary olrouli rolt circuits is .e

foibe" cathode ,thereby age response has a pronounced double Unlike the normal .1. F. transformers. preceding the limiter tube. the response curve .of the vpri n mary of the discriminator transformer is .of large importance. The pronounced, double.: hump responseof ,the primary provides a cor; rection for inherent central ,curvature in the normal frequency deviationys. voltage output? characteristiciof ,thedemodulator Analysis demonstrates that `the diodes vand rer .spectiye load resistors effectively act .as a `load on the primary .circuit vof .the .discrirrlinator sec? tion. The diode loading of the primary circuit or the diseriminator may, .in general, assu e suelo magnitudo .the .sain throiieh .tbedise .crirniiiatoris low. .i loading .depends .on a climber voi factors/ a .hielo I. valueisfueed, the ,discrimina cuits must have bien .effectire fQsi .to be selec.- tive enough.. and any ,loading io seitioiie- Avalue .of the load .resitors .below-eased Jtoo much, or vhum D' Islip iiolrooi t1.. f stents result, .lov la. @es of the .ois nator for ,higher a. ,frseiioiioioe ovliiob .periiiits noiseto oorrietr uen.

In aoooiflaiior with `oils f obieot .of .my invention o negative roeistoiroe oiie'ot is duced into the .discrirnin IceQ-,oo a'. invention., t, vtiro disorimiriator prima reduce I:tilde effects the 3 of received FM signal carrier with the result that the selectivity of the primary is a desirable function of received signal strength.

Still other objects of my invention are to improve amplitude limiter circuits for FM reception, and more particularly to provide a limiterdiscriminator network of desirable characteristics.

Still other features will best be understood .by reference to the following description, taken in connection with the drawing, in which I have indicated diagrammatically a circuit organization whereby my invention may be carried into effect.

In the drawing:

Fig. 1 shows one embodiment of the invention; and

Fig. 2 shows an equivalent circuit diagram of the discriminator circuit of Fig. 1.

Referring now to the figures of the accompanying drawings, wherein like reference letters and numerals designate similar circuit elements, there is shown in Fig. l so much of an FM receiver as is essential to a proper understanding of my invention. It is assumed that the limiter and demodulator of Fig. 1 are embodied in a superheterodyne receiver, since that form of receiver is most widely employed at present. The customary selective radio frequency amplifier, converter and intermediate frequency amplifier precede the tuned input transformer I which feeds the I. F. signals to the signal grid 2 of limiter tube 3. Those skilled in the art of radio communication, and more specifically FM communication, are fully aware of the details of circuit design prior to limiter tube 3. The received FM waves may have a carrier, or center, frequency in any of the known frequency bands allocated to FM or PM reception. The present FM broadcast range extends from 42 to 50 megacycles (ma). My invention, however, is not limited to operation in that band, but is readily adapted to the newly allocated 88-1-06 mc. band.

Assuming operation in the 42-50 mc. range,

the selector circuits of the receiver between the the acceptance of the overall 150 kc. frequency swing of a selected modulated carrier. The frequency variations of the signal energy are, of course, representative of the modulation applied to the carrier wave at the transmitter. Since a PM wave essentially differs from an FM Wave in that the extent of frequency deviation is proportionately high for the higher modulating frequencies, it will be clear that the FM receiver may be employed for detection of PM waves with de-emphasis correction subsequent to the demodulator.

Assuming, now, that there has been applied to the resonant primary circuit 4 of I. F. transformer I the FM energy whose center or carrier frequency has been reduced to the operating I. F. value of 4.3 mc., each of circuits 4 and 5 is tuned to the I. F. value. The frequency value of 4.3 mc. is illustrative, and can be changed to any other suitable magnitude. The circuits 4 and 5 are coupled to provide a band pass responsecharacteristic about 200 kc. wide. Limiting is accomplished by means of tube 3, shown as a pentode tube by way of specific illustration. The cathode 6, either indirectly or directly heated, is preferably connected directly to ground, while the low potential side of input circuit 5 is connected to ground by a. resistor R1 shunted by condenser C1. The magnitudes of components R1 and Ci are so chosen as to provide a relatively short time constant. For example, and in no way restrictive, R1 may -be 150,000 ohms while C1 may be 22 micro-microfarads (mmf.). The control grid 2 is connected to the high alternating potential side of circuit 5.

The plate or anode I of limiter tube 3 is connected to operate at a relatively low positive direct current potential. Thus, the plate 'I is connected through the resistor 8 to a point on a direct current source (not shown) having a potential of, for example, +250 volts. It will be ob served that between the +250 volts point and the plate 'I substantial resistance is deliberately introduced into the plate circuit to reduce the normal plate voltage to such a low positive value, say +70 volts, that the tube will readily saturate. The screen' grid 9 of tube 3 is connected to the +250 volts point through a resistor R whose upper end is bypassed to ground by condenser C. The values of R and C are so chosen that network R, C has a relatively short time constant. The normal no-signal voltage of the screen grid 9 will be relatively small. For example, the nosignal screen voltage may be as 10W as +70 volts. This screen voltage will increase when strong signals are present. As shown, the suppressor grid I0 is connected to cathode 6 within the tube envelope, and acts as a suppressor of secondary electrons emitted from plate 1.

The second stage of amplitude limiting is utilized to provide a substantial elimination of relatively rapid amplitude variations across the input terminals of the discriminator input network of the FM detector. The second limiter is generally constructed in the same manner as is the first limiter, but with certain changes now to ybe pointed out in detail. The tube I I is shown as of the pentode type, and has its cathode I2 connected to ground through an unbypassed resistor I3. Resistor I3 is unbypassed to permit the introduction of feedback voltage into the cathode. The control grid I4, upon which FM signals are impressed through condenser I5, is returned for direct currents to an intermediate point I6 on the cathode resistor I3. The leak resistor I'I connects tap I6 to the grid I4.

The screen grid I8 of tube Il is connected to the +S point of the direct current source through resistor I9, whose upper end is bypassed to ground for alternating current by condenser 20. The plate 2| of tube II is connected through the primary coil 22 to the +B point of the direct current source. Preferably the plate 2I should have full +250 volts applied thereto. The lower end of coil 22 is bypassed to ground by condenser 22. The primary coil 22 is shunted by condensers 23 and 24 connected in series relation, and the junction of condensers 23 and 24 is connected by lead 25 to the ungrounded end of cathode resistor I3.

It will be observed that the limiter tube II utilizes a cathode resistor to establish the operating bias point for grid I4. The screen voltage and plate voltage of the tube are so chosen that the tube functions as a limiter. The normal screen voltage of tube II is preferably A+70 volts.

'amar-2v The opera-ting bias forgrid UlA is so-cho'sen that half Acycles of the FM input potentials lmore* neg'- ative than a predetermined negative voltage vwill cause cut-cii of the plater current flow. Positive half cycles, duel to the relatively low 'screen and plate voltages will cause saturation. The effect of cascading the limiters will be-to provide a substantial elimination of response at the output of the FM detector to any vamplitude variation of signal at the antenna of the receiver. The leadA 25 provides a regenerative feedback path from the output circuit of tubeV Il. I Such a regenerative, or positive, feedback is electrically equivalent to providing a negative resistance across primary circuit 22, 23', 24. The advantages of such injectionV of negative resistance into the plate circuit of tube il will be explained at a later point. y The coils 22 and 25 are the respective primar and secondary windings of the discriminator transformer. VCoil 22 and condensers 23, 24 provide the resonant primary circuit P, while the secondary coil 2li and condenser 2l in parallel with it provide-the resonant secondary circuit S. Condensers 23 and 2t in series tune coil 22 to the Il. F; value. Circuit Sis, also, tuned to the operating I. F. value of 4.3 mc. Circuits P and S are preferably coupled so as to provide a substantially double-bumped response curve for the primary circuit P, while providing a band pass curve for the secondary circuit. The high alternating potential side of primary circuit P is connected to the mid-point of coil 26 through adirect current blocking condenser 28, which functions as a direct kconnection so far as the I. F. signal currents are concerned. In other words, condenser 28 imparts no phase shiftrto the I. F; currents applied to the mid-point of coil 26.

The circuits P and S constitute a discriminatorEv network of the type described in the aforesaid Seeley patent, and referred to herein as a Seeley discriminator. It is sufficient for the purposes of the present application to explain that at the instant when the applied I. F. energy has a frequency equal to tre resonant frequencies of circuits P and S, the signal voltage across circuit S will be 90 out of phase with the voltage across primary circuit P. This is due tothe magnetic coupling between resonant circuits P and S. However, the connection including condenser 28, will, also, inject into the circuit S primary signal voltage which has not been subjected to any phase shift.

Due to the fact that the primary voltage is applied to the mid-point of' coil 26, it will be lseen that from each end of coil 26 to ground there will exist primary signal voltage in phase quadrature with thev induced phase-shifted signal voltage.' The induced voltages in each half of the secondary coil ZG-are of opposite polarity. Hence, there will exist between each end of coil 2li-and ground a resultant voltage which is the vector sum of the phase quadrature-related voltages across each half of secondary winding 26 and the primary voltage; These resultant voltages will be of equal magnitude at the instant when the I. F. energy applied to circuit P is equal to the resonant frequencies of the discriminatol` circuits.-

Hou/even should the instantaneous signal frequency deviate or shift with respect to the predetermined reference frequencies of circuits P and S, then the resultant voltages at the opposite ends of coil il will become unequal because of phase changes away from the quadrature phase;

relation. The inequality will be dependent'upon the magnitude of frequency deviation from the referenceV frequency, while the direction of the inequality will depend upon the direction loffrequency devia-tion. In thisA way thereis derived from lthe frequency-variable waves a pair lof volt# ages which are equal in magnitude at the instant when the signal frequency is equalto the'discrimi nator reference frequency, but-which vary magnitude with respect to each otherv for fre*- quency deviations fronr the center frequency;r The function of the rectifier tube 28 is to prof videa pair Aof devices for rectifying the aforesaid pair of variable'voltages:

T-ube 2'8", while Vshown by wayvr of exampleas a Glilr type tube embodying a pair of separate diodes, maybe a pair of in'depedent diode tubes or othersuitablel rectiers; The anode 29" and cathodeV Sli'of the upper diode deviceV are con-lV nected between the'upper sid'eof circuit S'andthe upper end of load resistor 3l. Th'elower diode device 32:, 334 is connected between the groundedend of'load resistor 3E and the lower side of circuit S. The rnid-poird',V of secondary coil' 26' is connected by lead 35 to the junction of 1oad're`' sisters 3i and 3i'. Hence, theresultant I. F. Voltage applied to anode'twill be're'ctiiied', and the;` rectified voltage will' `appear across resistor 3l".

In the same way the-:resultant I. F. voltage applied to diode anode 32 will be rectified, and' the rected voltage will appearv across resistor 34'.` Since the rectified voltages across'resistors 3i' arid 34- are combined in polarity opposition relative to ground, the' resultant potential at the end 'of' resistorv 3i connected' to cathode 36' will*`r be zero atthe instant when the frequency of the applied FM waves is equal to the reference' frequencyA of' the discriininator` circuits P andSL andv willl vary in'rnagnitude` and polarity depending respectively upon the extent and direction'oi' frequency deviation: The resistors 3i and 34 are bypassed by a" suitabl'e. F. bypass condenser 36, Vand-the modulationfirequency'component of the resultant rectied voltage' is applied through resistor-condenser network 3l' to any-suitable iollowingaudiowfre? quency modulationamplier network which mayl be'followed' by a' suitable reproducer.

As' explained previously, it' is highly` desirable to. have the response curve of primary circuit P markedly double-humped. The secondary re` sponse curve S is relatively flat-topped withv some# what of al depression at its center. ln' practice, the transformer Iwindings 22' and 26 are coupled approximately to the critical coupling value. vIt should be noted that the primary 221s coupled to the diodes 29; 3B and 32, `l3'both through vthe transformer windings and through condenser 28. Becauseof the connection including condenser'28, thel response curve of the primary' circuit P (as well as of the secondary circuit S) is important to the operation of the discriminator. The'best overall discriminator characteristic,` both as to linearity and length, is obtained'when theresponse of the primary circuit Pis substantially in accordance with a double-humped curve. If now, there occurs `any flattening of the yprimary response' curve, the effect will be to change the overall discriminator performance in a highlyv undesirable manner since the linear portion of the discriminator characteristic becomes shortened, and the discriminator characteristic". is otherwisedeleteriously affected. y

It can be demonstrated thatV the two diodes 2li, 3l]A and 32, 33 and their load'resistors' produceV a" damping effectv onthe primary circuit?` which iSithe` equivalentv of 'that which would'y result ifa resistor' of approximately a small fraction of the value of load resistors 3| and 34 were placed directly in shunt across the primary circuit. In this connection, the action on the secondary circuit is only equivalent to the placing of a resistor of substantially higher value across the secondary circuit, so that the damping effect on the secondary is substantially less than on the primary. Therefore, the effect on the primary circuit P of increasing or decreasing the flow of current through the diodes is substantially greater than the action on the secondary circuit. It is readily seen that when the diodes are conductive, and current is iiowing through them, there exists a relatively small impedance across the primary circuit. In other words the equivalent series resistance in the primary circuit, which causes damping action, is relatively high since it is inversely related to the shunt load. It is this positive damping resistance which is disadvantageous, so far as the range of the linearity of the detection characteristic is concerned. The higher the value of the I. F. the more serious is the effect of diode loading.

In accordance with my present invention, the effect of the shunt positive resistance across primary circuit P is simply and effectively reduced by shunting the primary circuit with a negative resistance. This negative resistance is created by virtue of the regenerative feedback path 25. Condenser 24 is much larger than condenser 23, and the drop across condenser 24 is fed back to the cathode I2 of tube II. The cathode resistor I3 is unbypassed to permit the introduction of the feedback voltage into the cathode circuit. Hence, resistor I3 functions to provide the feedback Voltage that gives the regeneration. The amount of regenerative feedback is preferably so chosen as to nullify the undesired loading of the primary circuit. The degree of regenerative feedback is dependent on received signal intensity. Strong signals cause the effective transconductance of the tube to be reduced, because of the bias developed. This decreases regenerative feedback through lead 25 from the discriminator primary circuit P to the cathode resistor I3 of the limiter tube II. This is effectively equivalent to shunting the primary circuit with a negative resistance of decreased magnitude. As a result the positive resistance effectively shunted across the primary by the diode circuits is largely uncompensated, and the damping of the primary circuit P is relatively large. The selectively of the discriminator network P, S is broadened due to the damping, and the slope of the detection characteristic is caused to become less sharp. This is a desirable effect, since for strong signal reception noise and interference are relatively unimportant.

However, when weak signals are received the reverse action takes place. In the case of reception of weak FM signals (as in the case of an FM receiver in an automobile passing through an area tending to attenuate the FM signals), it is desirable to sharpen the discriminator selectivity thereby to reduce response to noise and interference. The amount of regenerative feedback is increased for weak signal reception. As a result, the magnitude of the negative resistance lacross the discriminator primary is increased, thereby counter-acting the effect of the shunt positive resistance provided by the diode circuits. This reduces the damping of the primary circuit and sharpens the response band of the discriminator. Hence, the magnitude of the negative resistance eiIect introduced across the discriminator primary is automatically adjustable in response to the received carrier strength. The regenerative feedback circuit acts, therefore, in the manner of an automatic selectivity control over the discriminator network.

Fig. 2 shows the equivalent of the discriminator circuit of Fig. 1. The shunt negative and positive resistances (respectively shown as -R and +R in dashed lines) are indicated. In this simple and effective manner I make it possible to correct for undesirable damping or loading of the discriminator primary without having to change the values of the load resistors and/or the Q of the discriminator coils. It is pointed out that when -R is shunted across' the primary circuit P, it affects chiefly the selectivity of the primary. However, the overall selectivity of P, S, is afrected depending on how tightly the secondary S is coupled to the primary P.

While I have indicated and described a system for carrying my invention into effect, it will be apparent to one skilled in the art that my invention is by no means limited to the particular organization shown and described, but that many modifications may be made without departing from the scope of my invention.

What I claim is:

1. In a frequency modulated carrier wave receiver, a carrier wave amplifier having a cathode, a control grid and an anode, means for impressing said carrier wave between said cathode and grid, an unbypassed resistor for connecting said cathode to a point of fixed potential, a frequency discriminator network coupled between said anode and a point of fixed potential, said network including a primary circuit resonant to the center frequency of said carrier wave, a balanced rectifier system effectively coupled across said primary circuit and causing excessive damping thereof, and a positive feedback connection between said cathode and an intermediate point of said primary circuit to reduce said damping and to maintain the linearity of the discriminator curve regardless of the strength of said carrier wave.

2. In a frequency modulated .carrier wave receiver, a limiter having input and output electrodes, a carrier wave amplifierhaving a cathode, a control grid and an anode, means for impressing said carrier wave between the input electrodes of said limiter, means for coupling the output electrodes of said limiter to said control grid and cathode to impress the limited carrier wave thereon, an unbypassed resistor for connecting said cathode to a point of fixed potential, a frequency discriminator network coupled between said anode and a point of fixed potential, said network including a primary circuit parallel resonant to the center frequency of said carrier wave and having a pair of serially connected capacitors, a balanced rectifier system effectively coupled across said primary circuit and causing excessive damping thereof, and a positive feedback connection between said cathode and the junction point of said pair of capacitors to reduce said damping and to maintain the linearity of the discriminator curve regardless of the strength of said carrier wave.

3. In a frequency modulated carrier wave rereceiver, a carrier wave limiter having a cathode, a control grid and an anode, means for impressing said carrier wave between said cathode and grid, an unbypassed resistor for connecting said cathode to a point of fixed potential, a frequency discriminator network coupled between said anode and a point of Xed potential, said network including a primary circuit parallel resonant to the center frequency of said carrier wave and having a pair of series connected capacitors, one of said capacitors having a. larger capacitance than the other one, a pair of balanced diode rectierseiectively coupled across said primary circuit and causing excessive damping thereof, and a connection between said cathode and the junction point of said pair of capacitors to feed back regeneratively the voltage drop across the larger one of said capacitors, thereby to reduce said damping and to maintain the linearity of the discriminator curve regardless of the strength of said carrier wave.

WIN'FIELD R. KOCH.

10 REFERENCES CITED The following references are of record in the le of this patent:

UNITED STATES PATENTS 

